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The previous post explained the datasheet of the precision capacitive touch/proximity sensor IC PCF8883, here we learn a typical circuit configuration using the same IC which can be applied in all products requiring precision remote touch stimulated operations.
 


The proposed capacitive touch and proximity sensor may be diversely used in many different applications as indicated in the following data:




A typical application configuration using the IC can be witnessed below:






The + input supply is attached with the VDD. A smoothing capacitor may be preferably connected across and VDD and ground and also across VDDUNTREGD and ground for more reliable working of the chip.

The capacitance value of COLIN as produced on pin CLIN fixes the sampling rate effectively. Increasing sampling rate may enable enhance reaction time on the sensing input with a proportionate increase in the current consumption

The sensing capacitive touch plate could be in the form of a miniature metal foil or plate shielded and isolated with a non conductive layer.

This sensing area could be either terminated over a longer distances via a coaxial cable CCABLE whose other ends may be linked with the IN of the IC, or the plate could be simply directly connected with the INpinout of the IC depending on the application needs.

The IC is equipped with an internal low pass filter circuitry which helps to suppress all forms of RF interferences that may try to make way in to the IC through the IN pin of the IC.

Additionally as indicated in the diagram one may also add an external configuration using RF and CF to further enhance the RF suppression and reinforce RF immunity for the circuit.

In order to achieve an optimal performance from the circuit, its recommended that the sum of the capacitance values of CSENSE + CCABLE + Cp should be within a given appropriate range, a good level could be around 30pF.

This helps the control loop to work in a better way with the static capacitance over CSENSE for equalizing the rather slower interactions on the sensing capacitive plate.


For achieving an increased levels of capacitive inputs it may be recommended to include a supplementary resistor Rc as indicated in the diagram which helps to control the discharge time as per the internal timing requirement specs.

The cross sectional area of the attached sensing plate or a sensing foil becomes directly proportional to the sensitivity of the circuit, in conjunction with the value of the capacitor Ccpc, reducing Ccpc value can greatly affect the sensitivity of the sensing plate. Therefore for achieving an effective amount of sensitivity, Ccpc could be increased optimally and accordingly.

The pinout marked CPC is internally attributed with a high impedance and therefore could be susceptible to leakage currents.

Make sure that Ccpc is chosen with a high quality PPC of MKT type of capacitor or X7R type for obtaining optimal performance from the design.

In case the system is intended to be operated with a restricted input capacitance of upto 35pF and at freezing temperatures -20 degrees C, then it may be advisable to bring down the supply voltage to the IC to around 2.8V. This in turn brings down the operating range of Vlicpc voltage whose specification lies between 0.6V to VDD - 0.3V.

Moreover, lowering the operating range of Vucpc could result in lowering the input capacitance range of the circuit proportionately.

Also, one may notice that as Vucpc value increases with decreasing temperatures as demonstrated in the diagrams, which tells us why appropriately lowering the supply voltage helps in decreasing temperatures.

Table 6 and Table7 indicates the recommended range of the components values which may be appropriately chosen as per the desired application specifications with reference to the above instructions.






Reference: PCF8883 data sheet

The IC PCF8883 is designed to work like a precision capacitive touch and proximity sensor switch through a unique (EDISEN patented) digital technology for sensing the minutest difference in the capacitance around its specified sensing plate.


The main features of this specialized capacitive touch and proximity sensor can be studies as given below:


 The following image shows the internal configuration of the IC PCF8883



The IC doesnt rely on the traditional dynamic capacitance mode of sensing rather detects the variation in the static capacitance by employing automatic correction through continuous auto-calibration.

The sensor is basically in the form of a small conductive foil which may be directly integrated with the relevant pinouts of the IC for the intended capacitive sensing or perhaps terminated to longer distances through coaxial cables for enabling accurate and effective remote capacitive touch sensing operations

The following figures represent the pinout details of the IC PCF8883. The detailed functioning of the various pinouts and the in-built circuitry may be understood with the following points:

A typical application configuration can be studied through this capacitive touch/proximity sensorcircuit design

The pinout IN which is supposed to be connected with the external capacitive sensing foil is linked with the ICs internal RC network.

The discharge time given by "tdch" of the RC network is compared by the discharge time of the second in-bult RC network denoted as "tdchimo".

The two RC networks go through periodic charging by VDD(INTREGD) through a couple of identical and synchronized switch networks, and subsequently discharged with the help of a resistor to Vss or the ground

The rate at which this charge discharge is executed is regulated by a sampling rate denoted by "fs".

In case if the potential difference is seen to be dropping below the internally set reference voltage VM, the corresponding output of the comparator tends to become low. The logic level which follows the comparators identifies the exact comparator that actually could switch before the other.

And if the upper comparator is identified to have fired first, this results with a pulse being rendered on CUP, whereas if the lower comparator is detected to have switched prior to the upper, then the pulse is enabled at CDN.


The above pulses engage in controlling the charge level over the external capacitor Ccpc associated with pin CPC. When a pulse is generated on CUP, the Ccpc is charged through VDDUNTREGD for a given period of time which triggers a rising potential on Ccpc.

Quite on the same lines, when a pulse is rendered at CDN, the Ccpc gets linked with current sink device to ground which discharges the capacitor causing its potential to collapse.

Whenever the capacitance at pin IN gets higher, it correspondingly increases the discharge time tdch, which causes the voltage across the relevant comparator to fall at a correspondingly longer time. When this takes place the output of the comparator tends to get low which in turn renders a pulse at CDN forcing the external capacitor CCP to discharge to some smaller degree.

This implies that CUP now generates the majority of the pulses which causes CCP to charge up even more without going through any further steps.

Inspite of this, the automatic voltage controlled calibration feature of the IC which relies on a sink current regulation "ism" associated with pin IN makes an effort to balance out the discharge time tdch by referring it with an internally set discharge time tdcmef.

The voltage across Ccpg is current controlled and becomes responsible for the discharge of the capacitance on IN rather rapidly whenever the potential across CCP is detected to be increasing. This perfectly balances the increasing capacitance on input pin IN.

This effect give rise to a closed loop tracking system which continuously monitors and engages into an automatic equalizing of the discharge time tdch with reference to tdchlmf.

This helps to correct sluggish variations in capacitance across IN pinout of the IC. During rapidly charging sates for example when a human finger is approached the sensing foil quickly, the discussed compensation might not transpire, in equilibrium conditions the length of the discharge period do not differ causing the pulse to alternately fluctuate across CUP and CDN.


This further implies that with larger Ccpg values a relatively restricted voltage variation for each pulse may be expected for CUP or CDN.

Therefore the internal current sink gives rise to a slower compensation, thereby enhancing the sensitivity of the sensor. On the contrary, when CCP experiences a decrease, causes the sensor sensitivity to go down.





An in-built counter stage monitors the sensor triggers and correspondingly counts the pulses across CUP or CDN, the counter gets reset each time the pulse direction across the CUP to CDN alternates or changes.
The output pin represented as OUT undergoes an activation only when adequate number of pulses across CUP or CDN  are detected. Modest levels of interference or slow interactions across the sensor or input capacitance does not produce any effect on the output triggering.


The chip makes note of several conditions such as unequal charge/discharge patterns so that a confirmed output switching is rendered and spurious detection are eliminated.


The IC includes an advanced start-up circuitry which enables the chip to reach equilibrium rather quickly as soon as the supply to it is switched ON.


Internally the pin OUT is configured as an open drain which initiates the pinout with a high logic (Vdd) with a maximum of 20mA current for an attached load. In case the output is subjected with loads over 30mA, the supply is instantly disconnected due to the short circuit protection feature which is instantly triggered.
This pinout is also CMOS compatible and therefore becomes appropriate for all CMOS based loads or circuit stages.

As mentioned earlier, the sampling rate parameter "fs" relates itself as 50% of the frequency employed with the RC timing network. The sampling rate can be set across a predetermined span by appropriately fixing the value of CCLIN.

An internally modulated oscillator frequency at 4% through a pseudo-random-signal inhibits any chance of interferences from surrounding AC frequencies.

The IC also features a useful "output state selection mode" which can be used for enabling the output pin to either in the monostable or bistable state in response to the capacitive sensing of the input pinout. Its rendered in the following manner:

Mode#1 (TYPE enabled at Vss): The output is rendered active for sp long as the input is held under the external capacitive influence.

Mode#2 (TYPE enabled at VDD/NTRESD): In this mode the output is alternately switched ON and OFF (high and low) in response to subsequent capacitive interaction across the sensor foil.

Mode#3 (CTYPE enabled between TYPE and VSS): With this condition the output pin is triggered (low) for some predetermined length of time in response to each capacitive touch inputs, whose duration is proportional to the value of CTYPE and can be varied with a rate of 2.5ms per nF capacitance.


A standard value for CTYPE for getting around a 10ms delay in mode#3 could be 4.7nF, and the maximum permissible value for CTYPE being 470nF, which may result in with a delay of about a second. Any abrupt capacitive interventions or influences during this period are simply ignored. 

Reference: PCF8883 data sheet

A simple touch sensor switch circuit can be built using a single IC 4017 and a few other passive components, the procedure is explained in the following article.


Referring to the below given circuit diagram for the proposed simple touch sensor switch, we can see that the entire design is built around the IC 4017 which is a 10 step johnsons decade counter divider chip.



The IC basically consists of 10 outputs, starting from its pin#3 and randomly ending at pin#11, constituting 10 outputs which are designed to produce a sequencing or shifting high logics across these output pins in response to every single positive pulse applied at its pin#14.

The sequencing does not need to finish at the last pin#11, rather could be assigned to stop at any desired intermediate pinout, and revert to the first pin#3 to initiate the cycle afresh.

This is simply done by connecting the end sequence pinout with the reset pin#15 of the IC. This makes sure that whenever the sequence reaches this pinout, the cycle stops here and reverts to pin#3 which is the initial pinout for enabling a repeat cycling of the sequence in the same order.

For example in our design pin#4 which is the third pinout in the sequence can be seen attached to pin#15 of the IC, implies that as the sequence jumps from pin#3 to the next pin#2, and then to pin#4 it instantly reverts or flips back to pin#3 to enable the cycle again.

This cycling is induced by touching the indicated touch plate which causes a positive pulse to appear at pin#14 of the IC each time its touched.

Lets assume at power switch ON the high logic is at pin#3, this pin is not connected anywhere and is unused, while pin#2 can be seen connected with the relay driver stage, therefore at this moment the relay stays switched OFF.

As soon as the touch plate is tapped, the positive pulse at pin#14 of the IC toggles the output sequence which now jumps from pin#3 to pin#2 enabling the relay to switch ON.

The position is held fixed at this point, with the relay in the switched ON position and the connected load activated.

However as soon as the touch plate is touched again, the sequence is forced to jump from pin#2 to pin#4, which in turn prompts the IC to revert the logic back to pin#3, shutting of the relay and the load and enabling the IC back to its standby condition.